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Frontiers of Optoelectronics

ISSN 2095-2759

ISSN 2095-2767(Online)

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Front. Optoelectron.    2018, Vol. 11 Issue (2) : 163-188    https://doi.org/10.1007/s12200-018-0813-1
REVIEW ARTICLE
Optical signal processing based on silicon photonics waveguide Bragg gratings: review
Saket KAUSHAL1, Rui Cheng2, Minglei Ma2, Ajay Mistry2, Maurizio Burla1,3, Lukas Chrostowski2(), José Azaña1()
1. Institut National de la Recherche Scientifique – Centre Energie, Matériaux et Télécommunications (INRS-EMT), Varennes, QC J3X 1S2 Canada
2. Department of Electrical and Computer Engineering, University of British Columbia (UBC), Vancouver, British Columbia, V6T 1Z4 Canada
3. Institute of Electromagnetic Fields, ETH Zurich, Gloriastrasse 35, Zurich 8092, Switzerland
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Abstract

This paper reviews the work done by researchers at INRS and UBC in the field of integrated microwave photonics (IMWPs) using silicon based waveguide Bragg gratings (WBGs). The grating design methodology is discussed in detail, including practical device fabrication considerations. On-chip implementations of various fundamental photonic signal processing units, including Fourier transformers, Hilbert transformers, ultrafast pulse shapers etc., are reviewed. Recent progress on WBGs-based IMWP subsystems, such as true time delay elements, phase shifters, real time frequency identification systems, is also discussed.

Keywords silicon photonics      ultrafast optical signal processing      integrated microwave photonics (IMWPs)     
Corresponding Author(s): Lukas Chrostowski,José Azaña   
Just Accepted Date: 04 June 2018   Online First Date: 02 July 2018    Issue Date: 04 July 2018
 Cite this article:   
Saket KAUSHAL,Rui Cheng,Minglei Ma, et al. Optical signal processing based on silicon photonics waveguide Bragg gratings: review[J]. Front. Optoelectron., 2018, 11(2): 163-188.
 URL:  
https://academic.hep.com.cn/foe/EN/10.1007/s12200-018-0813-1
https://academic.hep.com.cn/foe/EN/Y2018/V11/I2/163
Fig.1  (a) Cross-sectional view of silicon-on-insulator (SOI) wafer. (b) Common waveguides in silicon photonics. (Left) Strip waveguide, also known as channel waveguides, photonic wires, or ridge waveguides. (Right) Rib waveguide, also known as ridge waveguide or strip-loaded ridge waveguide; Reproduced from Ref. [14]
Fig.2  Schematic illustration of a typical side-wall waveguide Bragg grating (WBG). W: waveguide width; ΔW: corrugation width; Λ: grating period; N: number of the periods
Fig.3  A typical design flow of an integrated Bragg grating for a target spectral response
Fig.4  (a) Typical amplitude and phase response of a photonic Hilbert transformer. (b) Corresponding apodization profile of a fiber based Bragg grating, obtained using layer peeling algorithm. Reproduced from Ref. [29]
Fig.5  Schematic of cladding-modulated waveguide Bragg gratings (WBGs). Λ: period of the silicon cylinders; W: diameter of the silicon cylinder; d: distance of the silicon cylinders from the edge of the waveguide
Fig.6  (a) (Left) Schematic of grating duty-cycle modulation and (right) the relationship curve between duty cycle and k. (b) (Left) Schematic of side-wall miss-alignment modulation and (right) the relationship curve between the miss-alignment and k
Fig.7  (a) Schematic flow showing the process of mapping the apodization profile into grating structure, taken from Ref. [35]. (b) Schematic diagram illustrating a typical phase-modulated grating structure. (c) (Blue) Target Gaussian apodization profile and (red) phase modulation amplitude along the grating A(z). (d) Phase modulation profile along the grating. (e) d(i) distribution along the grating position, where the horizontal line represents the level of ΛG/2 (158 nm)
Fig.8  (a) Complex spectral response of the designed Hilbert transformer. (b) Required coupling coefficient profile. (c), (d) and (e) are the calculated spectral responses of the gating apodized by the phase modulation method, the side-wall misalignment modulation, and duty cycle modulation, respectively; the spectral calculation is based on the standard transfer matrix method upon the apodized grating structures; the black curves in these figures are the amplitude response of designed Hilbert transformer, shown for comparison
Fig.9  Spectral responses of photonic Hilbert transformers based on waveguide Bragg gratings (WBGs) with different corrugation widths, calculated by the transfer matrix method (TMM) method
Fig.10  (a) Compare of the band structures for uniform medium and 1-D photonic crystal. (b) Schematic illustration of how the band structure is related to the reflection band of a Bragg grating. (c) FDTD band structure analysis in Lumeical FDTD Solutions. (d) Band structure diagram for of a waveguide Bragg grating (WBG) with ΔW of 50 nm. (e) Fourier transform (magnitude) of the time domain signals at the band edge from the FDTD simulation for WBGs with different ΔW; the frequency range between the two peaks corresponds to the band gap width
Fig.11  k versus corrugation width ΔW calculated by the different approaches, with the experimental values of the gratings fabricated by electron-beam lithography included for the comparison
Fig.12  (a) Spectra of WBGs with different degrees of ΔW jitter effects applied. s: standard deviations of ΔW variations. (b) Spectra of WBGs fabricated with different grid sizes when the s of ΔW jitter is (left) 1 nm and (right) 3 nm
Fig.13  Frequency to time conversion using temporal chromatic dispersion. Reproduced from Ref. [53]
Fig.14  Incident (solid red curve) and reflected (dashed green curve) spectra superimposed on the scaled oscilloscope traces of the output temporal waveforms (solid black curve): (a) for in-phase incident pulses and (b) for π-phase-shifted incident pulses. (c) Spectrum (dashed green curve) and the scaled temporal waveform (solid black curve) of the reflected in-phase double pulse signal reconstructed through Fourier transform spectral interferometry (FTSI). (d) Phase of the reflected signal reconstructed through FTSI. Reproduced from Ref. [21]
Fig.15  Measured reflection spectral response of the fabricated phase-shifted waveguide Bragg grating (PS-WBG) compared with the ideal fractional Hilbert transformer (FHT) response in (a) magnitude and (b) phase. The top inset shows examples of Gaussian input pulse spectra. Reproduced from Ref. [18]
Fig.16  Time-domain experimental testing results. The figure shows the measured input pulse (solid line), simulated output pulse obtained by filtering the measured input pulse with an ideal Hilbert transformer (dashed line), and actual output pulse measured using Fourier transform spectral interferometry (FTSI) (circled line), for input pulses with full width at half-maximum (FWHM) durations of (a) 4 ps and (b) 1.5 ps. Reproduced from Ref. [18]
Fig.17  Schematic of a laterally apodized waveguide Bragg grating (WBG). Reproduced from Ref. [16]
Fig.18  (a)−(c) Simulated and (d)−(f) measured amplitude and phase spectral responses, (g)−(i) cross-correlation coefficients, and (j)−(l) comparison between the temporal responses of ideal HTs with the response from the fabricated devices to different Gaussian pulses for the integer (two top rows) and fractional (last row) photonic HTs. Reproduced from Ref. [16]
Fig.19  Pulse shaping by linear filtering: (a) time-domain view; (b) frequency-domain view
Fig.20  (a) (i) Spectra of the ultrashort pulse of 7.8 ps pulse width before and after propagation through the fabricated Mach-Zehdner interferometer (MZI) when the pulse carrier wavelength matches one of the MZIs peak transmission wavelengths. (ii) Time-domain intensity profiles of the input pulse, the measured output pulse, and the simulated ideal output. Phase profile of the measured output pulse is also shown. (b) (i) Spectra of the ultrashort pulse of 11 ps pulse width before and after propagation through the fabricated MZI when the pulse carrier wavelength matches one of the MZIs notch transmission wavelengths. (ii) Time-domain intensity profiles of the input pulse, the measured output pulse, and the simulated ideal output. (iii) and (iv) Intensity and phase profiles of the measured output pulse. Reproduced from Ref. [65]
Fig.21  (a) Schematic of the proposed pulse shaping device and its principle of operation. (b) Phase coding by tuning the waveguide length in the differential delay lines. (c) Amplitude coding by tuning the coupling length. Reproduced from Ref. [66]
Fig.22  Micrographs taken using a camera mounted on a microscope, from part of the fabricated devices with [(a) and (b), respectively] R = 5 µm and 3 µm; (c) and (d), respectively, the simulated and measured amplitude temporal response and power spectral response (PSR) of a device consisting of n = 10 identical cascaded couplers; (e) and (f), respectively, n = 20 identical cascaded couplers; and (g) and (h), respectively, n = 5 identical cascaded couplers with a shorter delay difference. Reproduced from Ref. [66]
Fig.23  Dual-phase-shifted waveguide Bragg grating (DPS-WBG) magnitude response (a), operation as phase shifting (PS) (b), and true-time delay (TTD) (c). Reproduced from Ref. [19]
Fig.24  (a) Complex (magnitude and phase) radio frequency (RF) response for different phase shift values. (b) Complex (magnitude and phase) RF response for different true time delay values. Reproduced from Ref. [19]
Fig.25  Schematic of the silicon WBG (PS-WBG) employed as a linear-optics frequency discriminator. TX port: transmission port; RX port: reflection port. Reproduced from Ref. [17]
Fig.26  Simulated (dashed line) and measured (solid line; a) linear optical transmission and (b) reflection spectral responses of the phase-shifted waveguide Bragg grating (PS-WBG); (c) and (d) zoom with overlapped optical single sideband carrier (OSSB+C) spectrum. The optical responses are normalized to the maximum. (e) Radio frequency (RF) response of transmission (TX) and reflection (RX) ports; (f) ACF, obtained from Eq. (10). Reproduced from. [17]
Fig.27  Estimated frequency (red dots) and corresponding error (blue dots). Reproduced from Ref. [17]
Fig.28  Experiment of dynamic frequency identification. (a) A radio frequency (RF) signal with unknown frequency content enters the photonic instantaneous frequency measurement (IFM) system. (b) Time-domain signal at the IFM output was amplitude-coded according to the time-varying frequency content of the input signal. (c) Instantaneous power was extracted by self-mixing and low-pass filtering. (d) Using the inverse amplitude comparison function (ACF), the RF frequency content was estimated in a dynamic manner. (e) Spectrogram of the frequency-hopping input sequence is shown for comparison. Reproduced from Ref. [17]
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